Decouples two sides, each in their own asynchronous clock domain, of a ready/valid handshake to allow back-to-back transfers without a combinational path between input and output, thus pipelining the path to improve concurrency and/or timing. Any FIFO depth is allowed, not only powers-of-2. The minimum input-to-output latency is 7 cycles when both clocks are plesiochronous.
Since a FIFO buffer stores variable amounts of data, it will smooth out irregularities in the transfer rates of the input and output interfaces, and when used in pipeline loops, can store enough data to prevent artificial deadlocks (re: Kahn Process Networks with bounded channels).
This module is a variation of the synchronous Pipeline FIFO Buffer, directly derived from Clifford E. Cummings' Simulation and Synthesis Techniques for Asynchronous FIFO Design, SNUG 2002, San Jose.
This FIFO supports having the input and output interfaces each on their own mutually asynchronous clock (without knowledge or restriction on their relative clock frequencies or phase). Using a FIFO for data tranfer between asynchronous clock domains allows multiple transfers to overlap with the CDC synchronization overhead. Once the CDC synchronization is done, all the previously written data in one clock domain can be freely read out in the other clock domain without further overhead.
Since the input and output interfaces are asynchronous to eachother, they
each have their own locally-synchronous clear reset signal. However, it
makes no sense to reset one interface only, as that would corrupt the
read/write addresses and duplicate or lose data. Both interfaces must be reset
together. Pick one interface reset as the primary reset, then synchronize
it into the clock domain of the other interface using a CDC
Synchronizer.
The synchronized reset will release after the primary reset, but that will cause no problems: if the input interface comes out of reset first, it can begin storing data until the FIFO is full. If the output interface comes out of reset first, it will remain idle as the FIFO will remain empty until the input interface stores a data item.
`default_nettype none
module CDC_FIFO_Buffer
#(
parameter WORD_WIDTH = 32,
parameter DEPTH = 512,
parameter RAMSTYLE = "M10K",
parameter CDC_EXTRA_STAGES = 0
)
(
input wire input_clock,
input wire input_clear,
input wire input_valid,
output reg input_ready,
input wire [WORD_WIDTH-1:0] input_data,
input wire output_clock,
input wire output_clear,
output wire output_valid,
input wire output_ready,
output wire [WORD_WIDTH-1:0] output_data
);
initial begin
input_ready = 1'b1; // Empty at start, so accept data
end
From the FIFO DEPTH, we derive the bit width of the buffer addresses and
construct the constants we work with.
`include "clog2_function.vh"
localparam WORD_ZERO = {WORD_WIDTH{1'b0}};
localparam ADDR_WIDTH = clog2(DEPTH);
localparam ADDR_ONE = {{ADDR_WIDTH-1{1'b0}},1'b1};
localparam ADDR_ZERO = {ADDR_WIDTH{1'b0}};
localparam ADDR_LAST = DEPTH-1;
The buffer itself is a synchronous dual-port memory with dual clocks: one
write port to insert data, and one read port to concurrently remove data,
each in their own clock domain. Typically this memory will be a dedicated
Block RAM, but can also be built from LUT RAM if the width and depth are
small, or even plain registers for very small cases. Set the RAMSTYLE
parameter as required.
NOTE: There will NEVER be a concurrent read and write to the same
address, so write-forwarding logic is not necessary, nor possible since
read_clock and write_clock are asynchronous. Guide your CAD tool as
necessary to tell it there will never be read/write address collisions, so
you can obtain the highest possible operating frequency.
We initialize the read/write enables to zero, signifying an idle system.
reg buffer_wren = 1'b0;
wire [ADDR_WIDTH-1:0] buffer_write_addr;
reg buffer_rden = 1'b0;
wire [ADDR_WIDTH-1:0] buffer_read_addr;
RAM_Simple_Dual_Port_Dual_Clock
#(
.WORD_WIDTH (WORD_WIDTH),
.ADDR_WIDTH (ADDR_WIDTH),
.DEPTH (DEPTH),
.RAMSTYLE (RAMSTYLE),
.USE_INIT_FILE (0),
.INIT_FILE (),
.INIT_VALUE (WORD_ZERO)
)
buffer
(
.write_clock (input_clock),
.wren (buffer_wren),
.write_addr (buffer_write_addr),
.write_data (input_data),
.read_clock (output_clock),
.rden (buffer_rden),
.read_addr (buffer_read_addr),
.read_data (output_data)
);
Since the buffer is a synchronous RAM, it takes a clock cycle before the
read data updates, so we pass along the read enable line (buffer_rden)
through a register to synchronize it and signal valid read data
(output_valid). However, the register needs separate control: for
example, when the output interface reads out the last item out of the
buffer, the output becomes invalid even though the buffer output is
unchanged.
reg update_output_valid = 1'b0;
Register
#(
.WORD_WIDTH (1),
.RESET_VALUE (1'b0)
)
output_data_valid
(
.clock (output_clock),
.clock_enable (update_output_valid),
.clear (output_clear),
.data_in (buffer_rden),
.data_out (output_valid)
);
The buffer read and write addresses are stored in counters, running in
separate clock domains, which both start at (and clear to) ADDR_ZERO.
Each counter can only increment by ADDR_ONE at each read or write, and
will wrap around to ADDR_ZERO if incremented past a value of DEPTH-1,
labelled as ADDR_LAST. The depth can be any positive number, not only
a power-of-2.
reg increment_buffer_write_addr = 1'b0;
reg load_buffer_write_addr = 1'b0;
Counter_Binary
#(
.WORD_WIDTH (ADDR_WIDTH),
.INCREMENT (ADDR_ONE),
.INITIAL_COUNT (ADDR_ZERO)
)
write_address
(
.clock (input_clock),
.clear (input_clear),
.up_down (1'b0), // 0/1 --> up/down
.run (increment_buffer_write_addr),
.load (load_buffer_write_addr),
.load_count (ADDR_ZERO),
.carry_in (1'b0),
// verilator lint_off PINCONNECTEMPTY
.carry_out (),
// verilator lint_on PINCONNECTEMPTY
.count (buffer_write_addr)
);
reg increment_buffer_read_addr = 1'b0;
reg load_buffer_read_addr = 1'b0;
Counter_Binary
#(
.WORD_WIDTH (ADDR_WIDTH),
.INCREMENT (ADDR_ONE),
.INITIAL_COUNT (ADDR_ZERO)
)
read_address
(
.clock (output_clock),
.clear (output_clear),
.up_down (1'b0), // 0/1 --> up/down
.run (increment_buffer_read_addr),
.load (load_buffer_read_addr),
.load_count (ADDR_ZERO),
.carry_in (1'b0),
// verilator lint_off PINCONNECTEMPTY
.carry_out (),
// verilator lint_on PINCONNECTEMPTY
.count (buffer_read_addr)
);
To distinguish between the empty and full cases, which both identically show as equal read and write buffer addresses, we keep track of each time an address wraps around to zero by toggling a bit. The addresses never pass eachother.
If the write address runs ahead of the read address enough to wrap-around and reach the read address from behind, the buffer is full and all writes to the buffer halt until after a read happens. We detect this because the write address will have wrapped-around one more time than the read address, so their wrap-around bits will be different.
Conversely, if the read address catches up to the write address from behind, the buffer is empty and all reads halt until after a write happens. In this case, the wrap-around bits are identical.
reg toggle_buffer_write_addr_wrap_around = 1'b0;
wire buffer_write_addr_wrap_around;
Register_Toggle
#(
.WORD_WIDTH (1),
.RESET_VALUE (1'b0)
)
write_wrap_around_bit
(
.clock (input_clock),
.clock_enable (1'b1),
.clear (input_clear),
.toggle (toggle_buffer_write_addr_wrap_around),
.data_in (buffer_write_addr_wrap_around),
.data_out (buffer_write_addr_wrap_around)
);
reg toggle_buffer_read_addr_wrap_around = 1'b0;
wire buffer_read_addr_wrap_around;
Register_Toggle
#(
.WORD_WIDTH (1),
.RESET_VALUE (1'b0)
)
read_wrap_around_bit
(
.clock (output_clock),
.clock_enable (1'b1),
.clear (output_clear),
.toggle (toggle_buffer_read_addr_wrap_around),
.data_in (buffer_read_addr_wrap_around),
.data_out (buffer_read_addr_wrap_around)
);
We need to compare the read and write addresses, along with their
associated wrap-around bits, to detect if the FIFO is full or empty and
then signal to the input or output interfaces to stall temporarily.
Therefore, we need to transfer the read address into the output_clock
domain, and the write address into the input_clock domain. We do this
with two CDC Word Synchronizers.
A read/write address is always valid, so we tie sending_valid high and
ignore sending_ready. Then, we loop receiving_valid into
receiving_ready so we start a new CDC word transfer as soon as the
current CDC word transfer completes. This configuration samples the address
continuously, as fast as the CDC word transfer happens. The synchronized
address at receiving_data remains steady between CDC word transfers.
It takes a few cycles to do the CDC word transfer, so when comparing the local read or write address with the synchronized counterpart from the other clock domain, we are comparing to a slightly stale version, lagging behind the actual value. However, since the addresses never pass eachother, this does not cause any corruption. The synchronized value eventually catches up, and any artificial empty/full buffer condition is cleared. At worst, this lag means having to specify a somewhat deeper FIFO to achieve the expected peak capacity, depending on input/output rates. However, not being restricted to powers-of-two FIFO depths minimizes this overhead.
wire [ADDR_WIDTH-1:0] buffer_write_addr_synced;
wire buffer_write_addr_wrap_around_synced;
wire buffer_write_addr_synced_valid;
CDC_Word_Synchronizer
#(
.WORD_WIDTH (ADDR_WIDTH + 1),
.EXTRA_CDC_DEPTH (0),
.OUTPUT_BUFFER_TYPE ("HALF"), // "HALF", "SKID", "FIFO"
.FIFO_BUFFER_DEPTH (), // Only for "FIFO"
.FIFO_BUFFER_RAMSTYLE () // Only for "FIFO"
)
write_to_read
(
.sending_clock (input_clock),
.sending_clear (input_clear),
.sending_data ({buffer_write_addr_wrap_around, buffer_write_addr}),
.sending_valid (1'b1),
// verilator lint_off PINCONNECTEMPTY
.sending_ready (),
// verilator lint_on PINCONNECTEMPTY
.receiving_clock (output_clock),
.receiving_clear (output_clear),
.receiving_data ({buffer_write_addr_wrap_around_synced, buffer_write_addr_synced}),
.receiving_valid (buffer_write_addr_synced_valid),
.receiving_ready (buffer_write_addr_synced_valid)
);
wire [ADDR_WIDTH-1:0] buffer_read_addr_synced;
wire buffer_read_addr_wrap_around_synced;
wire buffer_read_addr_synced_valid;
CDC_Word_Synchronizer
#(
.WORD_WIDTH (ADDR_WIDTH + 1),
.EXTRA_CDC_DEPTH (0),
.OUTPUT_BUFFER_TYPE ("HALF"), // "HALF", "SKID", "FIFO"
.FIFO_BUFFER_DEPTH (), // Only for "FIFO"
.FIFO_BUFFER_RAMSTYLE () // Only for "FIFO"
)
read_to_write
(
.sending_clock (output_clock),
.sending_clear (output_clear),
.sending_data ({buffer_read_addr_wrap_around, buffer_read_addr}),
.sending_valid (1'b1),
// verilator lint_off PINCONNECTEMPTY
.sending_ready (),
// verilator lint_on PINCONNECTEMPTY
.receiving_clock (input_clock),
.receiving_clear (input_clear),
.receiving_data ({buffer_read_addr_wrap_around_synced, buffer_read_addr_synced}),
.receiving_valid (buffer_read_addr_synced_valid),
.receiving_ready (buffer_read_addr_synced_valid)
);
Normally, there is a singular source of state in a design, and all inputs and outputs are synchronous with eachother, and thus a singular calculation of control. But since the state of this particular design is split across two asynchronous clock domains, we cannot make a reliable simultaneous calculation with both halves. Thus, each half does its own control calculations, using the "stale", synchronized signals from the other half.
The input interface inserts directly into the buffer, and only signals transfers to stop if the buffer is full.
reg full = 1'b0;
reg insert = 1'b0;
always @(*) begin
full = (buffer_read_addr_synced == buffer_write_addr) && (buffer_read_addr_wrap_around_synced != buffer_write_addr_wrap_around);
input_ready = (full == 1'b0);
insert = (input_valid == 1'b1) && (input_ready == 1'b1);
end
The buffer output is registered, so the output interface is necessarily
pipelined and works in parallel with the input interface. Keeping that
pipeline full and signalling to the read_address counter when an item is
removed from the buffer requires a separate little engine to continually
read from the buffer when possible.
Recall from above that output_valid is a registered version of
buffer_rden, matching the latency of a buffer read and signalling when
a buffer read has completed and new output_data is available.
We update output_valid and try to read from the buffer if the other end
of the output interface is ready (output_ready is high) or if
output_data is currently invalid, so even if output_ready is low, we
try and pre-load the output interface with valid data. A buffer read then
happens if the buffer is not empty. Otherwise, output_valid updates from
a buffer_rden which is necessarily low, because the buffer is empty, and
thus output_valid goes (or remains) low in the next cycle. If we can read
from the buffer, and output_ready is high, then we have removed an
item from the buffer.
reg empty = 1'b0;
reg remove = 1'b0;
always @(*) begin
empty = (buffer_read_addr == buffer_write_addr_synced) && (buffer_read_addr_wrap_around == buffer_write_addr_wrap_around_synced);
update_output_valid = (output_valid == 1'b0) || (output_ready == 1'b1);
buffer_rden = (empty == 1'b0) && (update_output_valid == 1'b1);
remove = (buffer_rden == 1'b1) && (output_ready == 1'b1);
end
Now that we have defined the possible operations on the FIFO datapath (insert and remove), we can define the datapath transformations, which are the edges between states. Or put otherwise: in which state(s) can the insert and/or remove operations happen, and what do they mean.
Here, we can insert when not full (load), and remove when not empty (unload).
reg load = 1'b0; // Inserts data into buffer.
reg unload = 1'b0; // Remove data from buffer.
always @(*) begin
load = (full == 1'b0) && (insert == 1'b1);
unload = (empty == 1'b0) && (remove == 1'b1);
end
Here, we increment the read/write addresses as necessary, enable a write to the buffer if we increment the write address, wrap-around the read/write addresses when they reach the end of the buffer, and record that by toggling their associated wrap-around bit.
always @(*) begin
increment_buffer_write_addr = (load == 1'b1);
increment_buffer_read_addr = (unload == 1'b1);
buffer_wren = increment_buffer_write_addr;
load_buffer_write_addr = (increment_buffer_write_addr == 1'b1) && (buffer_write_addr == ADDR_LAST [ADDR_WIDTH-1:0]);
load_buffer_read_addr = (increment_buffer_read_addr == 1'b1) && (buffer_read_addr == ADDR_LAST [ADDR_WIDTH-1:0]);
toggle_buffer_write_addr_wrap_around = (load_buffer_write_addr == 1'b1);
toggle_buffer_read_addr_wrap_around = (load_buffer_read_addr == 1'b1);
end
endmodule